Use Matlab Function pwelch to Find Power Spectral Density – or Do It Yourself
In my last post, we saw that finding the spectrum of a signal requires several steps beyond computing the discrete Fourier transform (DFT). These include windowing the signal, taking the magnitude-squared of the DFT, and computing the vector of frequencies. The Matlab function pwelch  performs all these steps, and it also has the option to use DFT averaging to compute the so-called Welch power spectral density estimate [3,4].
In this article, I’ll present some examples to show how to use pwelch. You can also “do it yourself”, i.e. compute spectra using the Matlab fft or other fft function. As examples, the appendix provides two demonstration mfiles; one computes the spectrum without DFT averaging, and the other computes the spectrum with DFT averaging.
We’ll use this form of the function call for pwelch:
The input arguments are:
x input signal vector
window window vector of length nfft
noverlap number of overlapped samples (used for DFT averaging)
nfft number of points in DFT
fs sample rate in Hz
For this article, we’ll assume x is real. Let length(x) = N. If DFT averaging is not desired, you set nfft equal to N and pwelch takes a single DFT of the windowed vector x. If DFT averaging is desired, you set nfft to a fraction of N and pwelch uses windowed segments of x of length nfft as inputs to the DFT. The |X(k)|2 of the multiple DFT’s are then averaged.
The output arguments are:
pxx power spectral density vector, W/Hz
f vector of frequency values from 0 to fs/2, Hz
The length of the output vectors is nfft/2 + 1 when nfft is even. For example, if nfft= 1024, pxx and f contain 513 samples. pxx has units of W/Hz when x has units of volts and load resistance is one ohm.
The following examples use a signal x consisting of a sine wave plus Gaussian noise. Here is the Matlab code to generate x, where sine frequency is 500 Hz and sample rate is 4000 Hz:
fs= 4000; % Hz sample rate Ts= 1/fs; f0= 500; % Hz sine frequency A= sqrt(2); % V sine amplitude for P= 1 W into 1 ohm. N= 1024; % number of time samples n= 0:N-1; % time index x= A*sin(2*pi*f0*n*Ts) + .1*randn(1,N); % 1 W sinewave + noise
The power of the sine wave into a 1-ohm load is A2/2 = 1 watt. In the following, examples 1 and 2 compute a single DFT, while example 3 computes multiple DFT’s and averages them. Example 4 calculates C/N0 for the spectrum of Example 3.
Example 1. Spectrum in dBW/Hz
We’ll start out with a rectangular window. Note the sinewave frequency of 500 Hz is at the center of a DFT bin to prevent spectral leakage . Here is the code to compute the spectrum. Since we are not using DFT averaging, we set noverlap= 0:
nfft= N; window= rectwin(nfft); [pxx,f]= pwelch(x,window,0,nfft,fs); % W/Hz power spectral density PdB_Hz= 10*log10(pxx); % dBW/Hz
The resulting spectrum is plotted in Figure 1, which shows the component at 500 Hz with amplitude of roughly -6 dBW/Hz. How does this relate to the actual power of the sinewave for a 1-ohm load resistance? To compute the power of the spectral component at 500 Hz, we need to convert the amplitude in dBW/Hz to dBW/bin as follows. First, convert W/Hz to W/bin:
Pbin (W/bin) = pxx (W/Hz) * fs/nfft (Hz/bin) (1)
Then, we have in dB:
PdB_bin = 10*log10(pxx*fs/nfft) dBW/bin (2)
Or PdB_bin = PdB_Hz + 10*log10(fs/nfft) dBW/bin
If we set the noise amplitude to zero, we get PdB_Hz = -5.9176 dB/Hz and
PdB_bin= -5.9176 dBW/Hz + 10log10(4000/1024) = 0 dBW = 1 watt
So we are reassured that the amplitude of the spectrum is correct. This motivates us to try the next example, which displays the spectrum in dBW/bin.
Figure 1. Spectrum in dBW/Hz
Example 2. Spectrum in dBW/bin
To find the spectrum in dBW/bin, the code is the same as Example 1, except we use Equation 2 to find PdB_bin:
nfft= N; window= rectwin(nfft); [pxx,f]= pwelch(x,window,0,nfft,fs); % W/Hz power spectral density PdB_bin= 10*log10(pxx*fs/nfft); % dBW/bin
The spectrum is shown in the top plot of Figure 2. As expected, the component at 500 Hz has power of 0 dBW. Note that the amplitude of a sine’s spectral component in dBW/bin is constant vs nfft, while the amplitude in dBW/Hz varies vs. nfft. If we now replace the rectangular window with a hanning window:
We get the spectrum in the bottom plot of Figure 2. The peak power is now less than 0 dBW, because the power is spread over several frequency samples of the window. Nevertheless, this is a more useful window than the rectangular window, which has bad spectral leakage when f0 is not at the center of a bin.
Figure 2. Spectra in dBW/bin Top: rectangular window
Bottom: hanning windowExample 3. DFT averaging
For this example, fs, Ts, f0, A, and nfft are the same as for the previous examples, but we use N= 8*nfft time samples of x. pwelch takes the DFT of Navg = 15 overlapping segments of x, each of length nfft, then averages the |X(k)|2 of the DFT’s. The segments of x are shown in Figure 3, where we have set the number of overlapping samples to nfft/2 = 512.
In general, if there are an integer number of segments that cover all samples of N, we have :
(Navg – 1)*D + nfft = N (3)
Where D = nfft – noverlap. For our case, with D = nfft/2 and N/nfft = 8, we have
Navg = 2*N/nfft -1 = 15.
For a given number of time samples N, using overlapping segments lets us increase Navg compared with no overlapping. In this case, overlapping of 50% increases Navg from 8 to 15. Here is the Matlab code to compute the spectrum:
nfft= 1024; N= nfft*8; % number of samples in signal n= 0:N-1; x= A*sin(2*pi*f0*n*Ts) + .1*randn(1,N); % 1 W sinewave + noise noverlap= nfft/2; % number of overlapping time samples window= hanning(nfft); [pxx,f]= pwelch(x,window,noverlap,nfft,fs); % W/Hz PSD PdB_bin= 10*log10(pxx*fs/nfft); % dBW/bin
The resulting spectrum is shown in Figure 4. Compared to the no-averaging case in Figure 2, there is less variation in the noise floor. DFT averaging reduces the variance σ2 of the noise spectrum by a factor of Navg, as long as noverlap is not greater than nfft/2 .
Figure 3. Overlapping segments of signal x for N = 8*nfft and noverlap = nfft/2 (50%).
Figure 4. Spectrum with Navg = 15 and noverlap= nfft/2= 512.
Example 4. Calculation of C/N0
Reducing the noise variance by DFT averaging makes calculation of the noise level and thus carrier-to-noise ratio (C/N) more accurate. Let’s calculate C/N0 for the signal of Example 3, where N0 is the noise power in a 1 Hz bandwidth.
First, we’ll find the power of the sinewave (the “C” in C/N0) by performing a peak search on the dBW/bin spectrum, then adding the spectral components near the peak to get the total power. This is necessary because windowing has spread the power over several frequency samples.
y= max(PdB_bin); % peak of spectrum k_peak= find(PdB_bin==y); % index of peak Psum= fs/nfft * sum(pxx(k_peak-2:k_peak+2)); % W sum power of 5 samples C= 10*log10(Psum) % dBW carrier power
The peak power of 0 dBW is shown by the marker in the left plot of Figure 4. Now we’ll find N0 from the dBW/Hz spectrum. Choosing f = 800 Hz, we have:
PdB_Hz= 10*log10(pxx); % dBW/Hz f1= 800; % Hz k1= round(f1/fs *nfft); % index of f1 No= PdB_Hz(k1) % dBW/Hz Noise density at f1
The N0 marker is shown in the right plot of Figure 4. Figure 5 combines the dBW/bin and dBW/Hz plots in one graph. C/N0 is just:
CtoNo= C - No; % dB (1 Hz)
Figure 5. Left: Spectrum in dBW/bin with marker showing the power of the sinewave.
Right: Spectrum in dBW/Hz with marker at 800 Hz showing N0.
Figure 6. Spectrum in dBW/bin (blue) and dBW/Hz (grey).
Appendix Matlab Code to compute spectra without using pwelch
These examples use the Malab fft function to compute spectra. See my earlier post  for derivations of the formulas for power/bin and normalized window function.
Demonstrate Spectrum Computation/ No Averaging
%spectrum_demo.m 1/3/19 Neil Robertson % Use FFT to find spectrum of sine + noise in units of dBW/bin and dBW/Hz. fs= 4000; % Hz sample frequency Ts= 1/fs; f0= 500; % Hz sine frequency A= sqrt(2 % V sine amplitude for P= 1 W into 1 ohm. N= 1024; % number of time samples nfft= N; % number of frequency samples n= 0:N-1; % time index % x= A*sin(2*pi*f0*n*Ts) + .1*randn(1,N); % 1 W sinewave + noise w= hanning(N); % window function window= w.*sqrt(N/sum(w.^2)); % normalize window for P= 1 xw= x.*window'; % apply window to x % X= fft(xw,nfft); % DFT X= X(1:nfft/2); % retain samples from 0 to fs/2 magsq= real(X).^2 + imag(X).^2; % DFT magnitude squared P_bin= 2/nfft.^2 * magsq; % W/bin power spectrum into 1 ohm P_Hz= P_bin*nfft/fs; % W/Hz power spectrum % PdB_bin= 10*log10(P_bin); % dBW/bin PdB_Hz= 10*log10(P_Hz); % dBW/Hz % k= 0:nfft/2-1; % frequency index f= k*fs/nfft; % Hz frequency vector % % plot(f,PdB_bin),grid axis([0 fs/2 -60 10]) xlabel('Hz'),ylabel('dBW/bin') title('Spectrum with amplitude units of dBW/bin') figure y= max(PdB_Hz); plot(f,PdB_Hz),grid axis([0 fs/2 y-60 y+10]) xlabel('Hz'),ylabel('dBW/Hz') title('Spectrum with amplitude units of dBW/Hz')
Demonstrate Spectrum Computation with Averaging
Suppose we have segmented a signal x into four segments of length nfft, that could be overlapped. If we window each segment and take its DFT, we have four DFT’s as shown in Table A.1. Here, we have defined M= nfft and we have numbered the FFT bins from 1 to M (instead of 0 to M - 1).
Table A.1 DFT’s of four segments of the signal x.
Now we form the magnitude-squared of each bin of the four DFT’s, as shown in Table A.2 If we then sum the magnitude-square values of each bin over the four DFT’s and divide by 4, we obtain the average magnitude-squared value, as shown in the right column. Finally, we scale the magnitude-squared value to obtain the averaged power per bin  or averaged power per Hz:
Pbin(k) = 2/M2 * sum(|Xk|2)/4 W/bin (A.1)
PHz(k)= Pbin(k)*M/fs W/Hz (A.2)
PHz(k)= 2/(M*fs) * sum(|Xk|2)/4 W/Hz (A.3)
PHz(k) is the Welch power spectral density estimate.
Table A.2 Magnitude-square values of Four DFT’s, and their average (right column).
The following example m-file uses Navg = 8, summing 8 values of each |X(k)|2 and dividing by 8. For simplicity, noverlap = 0 samples. Another option for averaging, useful for the case where DFT’s are taken continuously, is exponential averaging, which basically runs the |X(k)|2 through a first-order IIR filter .
%spectrum_demo_avg 1/3/19 Neil Robertson % Perform DFT averaging on signal = sine + noise % noverlap = 0 % Given signal x(1:8192), % % |x(1) x(1025) . . . . x(7169)| % |x(2) x(1026) . . . . x(7170)| % xMatrix= | . . . | % | . . . | % |x(1024) x(2048) . . . . x(8192)| % % fs= 4000; % Hz sample frequency Ts= 1/fs; f0= 500; % Hz sine frequency A= sqrt(2 % V sine amplitude for P= 1 W into 1 ohm nfft= 1024; % number of frequency samples Navg= 8; % number of DFT's to be averaged N= nfft*Navg; % number of time samples n= 0:N-1; % time index x= A*sin(2*pi*f0*n*Ts) + .1*randn(1,N); % 1 W sinewave + noise w= hanning(nfft); % window function window= w.*sqrt(nfft/sum(w.^2)); % normalize window for P= 1 W % % Create matrix xMatrix with Navg columns, % each column a segment of x of length nfft xMatrix= reshape(x,nfft,Navg); magsq_sum= zeros(nfft/2); for i= 1:Navg x_column= xMatrix(:,i); xw= x_column.*window; % apply window of length nfft X= fft(xw); % DFT X= X(1:nfft/2); % retain samples from 0 to fs/2 magsq= real(X).^2 + imag(X).^2; % DFT magnitude squared magsq_sum= magsq_sum + magsq; % sum of DFT mag squared end mag_sq_avg= magsq_sum/Navg; % average of DFT mag squared P_bin= 2/nfft.^2 *mag_sq_avg; % W/bin power spectrum P_Hz= P_bin*nfft/fs; % W/Hz power spectrum PdB_bin= 10*log10(P_bin); % dBW/bin PdB_Hz= 10*log10(P_Hz); % dBW/Hz k= 0:nfft/2 -1; % frequency index f= k*fs/nfft; % Hz frequency vector % plot(f,PdB_bin),grid axis([0 fs/2 -60 10]) xlabel('Hz'),ylabel('dBW/bin') title('Averaged Spectrum with amplitude units of dBW/bin') figure plot(f,PdB_Hz),grid axis([0 fs/2 -60 10]) xlabel('Hz'),ylabel('dBW/Hz') title('Averaged Spectrum with amplitude units of dBW/Hz')
- Robertson, Neil, “Evaluate Window Functions for the Discrete Fourier Transform” https://www.dsprelated.com/showarticle/1211.php
- Mathworks website https://www.mathworks.com/help/signal/ref/pwelch.html
- Oppenheim, Alan V. and Shafer, Ronald W., Discrete-Time Signal Processing, Prentice Hall, 1989, pp. 737—742.
- Welch, Peter D., “The Use of Fast Fourier Transform for the Estimation of Power Spectra: A Method Based on Time Averaging Over Short, Modified Periodograms”, IEEE Trans. Audio and Electroacoustics, vol AU-15, pp. 70 – 73, June 1967. https://www.utd.edu/~cpb021000/EE%204361/Great%20DSP%20Papers/Welchs%20Periodogram.pdf
- Lyons, Richard G., Understanding Digital Signal Processing, 2nd Ed., Prentice Hall, 2004, section 3.8.
- Oppenheim and Shafer, p. 738.
- Robertson, Neil, “The Power Spectrum”, https://www.dsprelated.com/showarticle/1004.php
- Lyons, section 11.5.
Neil Robertson January, 2019
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Evaluate Window Functions for the Discrete Fourier Transform
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Compute the Frequency Response of a Multistage Decimator
Thanks Neil for the very informative article. I'm just wondering at the end where you calculate the SNR, should you have taken the processing gain into account. The noise floor as shown in figure 6 is lowered by the processing gain?
In figure 6, the left plot has amplitude units of dBW/bin, and the right plot has amplitude units of dBW/Hz. This is the reason for the difference in noise floor (and difference in carrier level as well).
Regarding processing gain due to DFT averaging: If you look at the un-averaged spectrum in Figure 2, and you try to put a marker on the noise, you can get a 20 dB variation of the noise reading depending on exactly where you place the marker. In the averaged spectrum of figure 5 and 6, we have less variation in the noise floor, so maybe only 6 dB variation. You can say processing gain is inherent in the plotted spectrum.
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